Method for generating measuring signals for measuring transmission properties of transmission links mutually influencing one another with crosstalk in telecommunications systems, particularly of handsfree equipment

ABSTRACT

In order to be able to measure the transmission properties of transmission links mutually influencing one another with crosstalk in electrical message systems, particularly of handsfree equipment (FSE) such that the measurement is not falsified by occurring crosstalk influences, measuring signals that are essentially orthogonal are generated in the time or frequency domain in the measuring system (MS) from respectively at least two voice or test signals.

BACKGROUND OF THE INVENTION

The present invention is directed to a method for generating measuring signals for measuring the transmission properties of handsfree telecommunications devices. Handsfree equipment in telephones are electrical message systems comprising specific transmission links for voice transmission wherein the transmission links are mutually influenced by crosstalk. The possibility of being able to “talk handsfree” with a telephone significantly enhances the operating comfort of a telephone and the quality of a telephone call. Handsfree devices enable call situations like those that occur in natural conversation between talking parties and allow a significantly greater freedom of movement and action of the person speaking handsfree. Voice-controlled signal processing mechanisms are utilized in order, on the one hand, to get control of the discussion and listening-in conditions that clearly deteriorate compared to ordinary handset-bound telecommunication and, on the other hand, to minimize the risk of occurring feedback. As is known, the voice-controlled signal processing in handsfree telephones ensues by

1) voice-dependently switched attenuations in the respective transmission and reception paths (attenuation control of the transmission and reception paths; principle of the level scale),

2) dynamic compression methods,

3) frequency-selective level scales,

4) decorrelation of the transmission and reception signals, and

5) adaptive compensation of acoustic echos.

Over and above this, the phenomenon of double talk is a critical feature of handsfree devices. The remote subscribers communicating with one another can thereby talk simultaneously. Of the aforementioned methods employed in handsfree devices for signal processing, adaptive compensation of acoustic echos (constructing adaptive echo compensators) in handsfree devices especially leads to a considerably reduced attenuation boost of the respectively employed level scale. Double talk only becomes possible as a result thereof because, transmission and reception paths are simultaneously active on principle. However, the utilization of echo compensators does not yet assure an unproblematical double talk mode because the adaption algorithms that are employed react more or less sensitively to changes in the room (place at which the handsfree telephone is put) and disturbances due to double talk phases. Moreover, the finite adaption speed may result in a disturbing increase or too slow a decrease of the echos under certain circumstances. It is precisely the double talk occurring in handsfree devices that is greatly deteriorated by the aforementioned signal processing mechanisms. So that true-to-life conversations (acquisition of the real double talk call situation) can be realized with the handsfree devices, the auditively relevant parameters must, on the one hand, be extracted, and the instrumentally measurable, technical parameters that describe the handsfree device must be acquired. Instrumentally measurable parameters for characterizing the conversation parameters of a handsfree device are not contained in measurement rules currently under discussion—such as, for example, the publication prI-ETS 300-245-3, Part 3; PCM A-Law, Loudspeaking and Handsfree Telephony, Stockholm, November 1994 (approval regulation). No measurements whatsoever are specified either for the double talk parameters or for the attenuation control of the two transmission paths (transmission and reception paths). In order to nonetheless be able to make statements at all with respect to the conversation parameters of handsfree devices, it is at least necessary that, first, the attenuation boost realized in a handsfree device designed in conformity with the indicated approval regulation and, second, the attenuation distribution on the two transmission paths of the handsfree device in the quiescent condition are known. Neither statements that characterize the behavior of the handsfree device during a double talk event nor farther-reaching analyses of the transmission quality during the double talk event are possible with these two parameters because other technical parameters such as, for example, the prioritization of voice direction, switching times, blocking times, etc., play a part therein. In order to acquire the behavior of voice-controlled devices quite generally dependent on the time and level conditions of the two input signals, the publication Fortschritte der Akustik—DAGA 1993, Bad Honnef, DPG GmbH, pages 932-935; F. Kettler, “Neue Messmethodik zur Bestimmung der Übertragungseigenschaften von Sprachechokompensatoren in Fernsprechnetz für Enzelmessungen und Tandemschaltungen” discloses that two “composite source” signals with different cycle durations be employed. A suitable simulation and analysis of a time segment is thereby possible, whereby the two signals are simultaneously fed in (true double talk). Whether one voice path is prioritized, whether both voice paths are attenuated in alternation or, for example, whether a fixed attenuation distribution of both paths during double talk is present can be determined from the transmitted sequence.

FIG. 1 shows a measuring arrangement MA constructed according to ITU (International Telecommunication Union) publication Volume V—RECOMMENDATION P.34, Melbourne, 1988, pages 64 through 71, particularly Ch. 6, for measuring the transmission properties of a handsfree device FSE or a handsfree telephone FST in the “double talk” call situation. To this end, the handsfree device FSE is connected to a handsfree loudspeaker FL in a transmission direction (transmission path) via a first amplifier V1. In a reception direction (reception path), a handsfree microphone FM is connected to the handsfree device FSE via a second amplifier V2. Given the illustrated measuring arrangement MA, the double talk call situation occurring during handsfree calling is achieved in that an “artificial ear” KO and an “artificial mouth” KM are allocated to the handsfree loudspeaker FL and to the handsfree microphone FM, respectively, for simulating the handsfree conditions. The measuring arrangement MA also contains a measuring system MS in order to be able to acquire transmission properties of the handsfree device FSE. For simulating the real handsfree conditions, this measuring system MS supplies the handsfree device FSE with, first, a “remote” first transmission signal (measured signal) SS₁ via a transmission/reception duplexer SEW preceding the handsfree device FSE that proceeds via the handsfree loudspeaker FL to the “artificial ear” KO and, second, supplies it with a “near” second transmission signal (measured signal) SS₂ via the “artificial mouth” KM and the handsfree microphone FM. In the present case, the signals SS₁, SS₂ are preferably selected such that their properties correspond to those of a natural voice signal (for example, crest factor, envelope, spectral composition, etc.).

The measurement of the transmission properties of the handsfree device FSE is implemented in the measuring system MS. To that end, the signals SS₁, SS₂ sent from the measuring system MS are compared to a first reception signal ES₁ received by the measuring system MS via the “artificial ear” KO and to a second reception signal ES₂ received by the measuring system MS via the transmission/reception duplexer SEW.

Analogous to the real handsfree conditions, the known crosstalk phenomenon occurs in the present measuring arrangement due to the infeed of the signals SS₁, SS₂. This crosstalk is expressed therein that a first crosstalk signal ÜS₁ related to the first transmission signal SS1 (for example, due to measuring arrangement and signal propagation properties) proceeds into the handsfree microphone FM in addition to the second transmission signal SS₂, and that a second crosstalk signal ÜS₂ related to the second transmission signal SS₂ (for example, due to measuring arrangement and signal propagation properties) proceeds into the “artificial ear” KO in addition to the first transmission signal SS₁. However, the measurement of the transmission properties of the handsfree device FSE is falsified by this crosstalk (undesired effect). Since crosstalk is fundamentally unavoidable in handsfree calling, efforts have therefore been made to acquire the influences of the crosstalk in order to be able to take the results resulting therefrom into consideration in the construction of the handsfree devices.

Given extremely simply constructed handsfree devices, wherein a frequency-independent level scale is employed, the measurement of the transmission properties of the handsfree device FSE can be undertaken with two mono-frequency signals differing in frequency.

When, however, telephones with modern handsfree devices (adaptive filter, dynamic characteristics matching, noise suppression, etc.) are to be measured, then the signals must have the properties of natural speech (for example, crest factor, envelope, spectral composition, etc.) both in the time domain as well as in the frequency domain.

SUMMARY OF THE INVENTION

An object of the present invention is to generate measuring signals for measuring systems for measuring the transmission properties of transmission links that mutually influence one another due to crosstalk, particularly of handsfree devices, such that the measurement of the transmission properties is not falsified by occurring crosstalk influences.

This object is achieved in accordance with the invention in a method of generating a plurality k of source signals s;

defining a (k−n+1)^(th) source signal length x_(k−n+1) of a (k−n+1)^(th) source signal S_(k−n+1) with x_(k−n+1) signal parts

a ₁ _(k−n+1) , a ₂ _(k−n+1) , a ₃ _(k−n+1) . . . a _(x) _(k−n+1) ⁻¹ , a _(x) _(k−n+1) ,

said source signal length x being x 0, and said coefficient n being n {2 . . . k};

defining a k^(th) source signal length x_(k) of a k^(th) source signal s_(k) with x_(k) signal parts

a ₁ _(k) , a ₂ _(k) , a ₃ _(k) . . . a _(x) _(k) ⁻¹ , a _(x) _(k) ;

calculating a measuring signal length m as m=n′m′, said n being n′ 0 and said m′ being m′=2^(ent((ld(max{x) ^(_(k−n+1)) ^(, x) ^(_(k)) ^(}))+0.5);

lengthening said (k−n+1)^(th) source signal s_(k−n+1) to said measuring signal length m by attaching m−x_(k−n+1) zeros to an end of said (k−n+1)^(th) source signal s_(k−n+1);

lengthening said k^(th) source signal s_(k) to said measuring signal length m by attaching m−x_(k) zeros to an end of said k^(th) source signal s_(k); and

modifying said lengthened (k−n+1)^(th) source signal s_(k−n+1), and said lengthened k^(th) source signal s_(k) such that said (k−n+1)^(th) source signal s_(k−n+1) and said k^(th) source signal s_(k) being essentially orthogonal.

The idea underlying the invention is comprised therein that measuring signals (for example, the transmission signals SS1, SS2 of FIG. 1) that are essentially orthogonal are generated from respectively at least two voice or test signals (“k=2” source signals) in the time or frequency domain in the measuring system for measuring the transmission properties of transmission links that mutually influence one another due to crosstalk, particularly of handsfree devices. The remaining properties of the measuring signals are defined by the properties of the voice or test signals employed. Preservation of the properties is important in order to be able to investigate the dynamic behavior of transmission links that mutually influence one another due to crosstalk, particularly the handsfree devices, with real voice signals or specific test signals.

The orthogonality relationship is thereby not used in the mathematically exact sense, i.e. two vectors x, y of a Euclidean vector space V are orthogonal exactly when (x, y)=0 applies, but in a version de-intensified to finite precision: two vectors x, y of a Euclidean vector space V are orthogonal when—analogous to claim 2—|x, y|<<|x| |x, y|<<|y| apply.

The object of the invention is also achieved in a device having a measuring system operating according to the method.

BRIEF DESCRIPTION OF THE FIGURES

FIG. 1 is a schematic diagram of a measuring arrangement measuring transmission properties of a handsfree device.

FIG. 2 shows a flowchart for measuring the transmission properties of handsfree devices in accordance with the present invention.

FIGS. 3-11 show graphs of the simulation of the measuring event in the measuring system.

DETAILED DESCRIPTION OF THE INVENTION

FIG. 2 IS a flowchart for measuring the transmission properties of the handsfree device FSE of FIG. 1, as installed in the measuring system MS of FIG. 1 and used for the measurement. To this end, the measuring system MS preferably comprises known components, which are not shown, such as, for example a microprocessor, a memory, A/D converters, D/A converters and program modules that are connected to one another for measuring the transmission properties of the handsfree device FSE according to the flowchart and correspondingly collaborate.

According to the plurality of measuring signals to be generated in conformity with the two transmission signals SS₁, SS₂ according to FIG. 1, two (k=2) source signals, a first source signal US₁ according to FIG. 3 and a second source signal US₂ according to FIG. 4 presented, for example, in the time domain are supplied to the measuring system MS or are input into the measuring system MS in a first method step VS1. The plurality “k”, however, can also be greater than “2”. This case occurs when—differing from the conditions given handsfree calling or given the handsfree device FSE according to FIG. 1 (transmission path and reception path that mutually influence one another due to crosstalk)—the transmission properties of more than two transmission links mutually influencing one another due to crosstalk are to be acquired through measurement. The following remarks apply for k 2.

In a second method step VS2 following thereupon, the respective length of the source signals US₁, US₂ is identified. To this end, for example, the number of coefficients or samples of the two source signals US₁, US₂ is respectively determined. Thus, for example: US₁ = {a_(1_(k − n + 1)), a_(2_(k − n + 1)), a_(3_(k − n + 1))  …  a_(x_(k − n + 1) − 1), a_(x_(k − n + 1))}  with  k = 2  and  n ∈ (2  …  k} ${US}_{1} = {\left\{ {a_{1_{1}},a_{2_{1}},{a_{3_{1}}\quad \ldots \quad a_{x_{1} - 1}},a_{x_{1}}} \right\} \quad \underset{\_}{{{length}\quad {of}\quad {US}_{1}} = x_{1}}}$ US₂ = {a_(1_(k)), a_(2_(k)), a_(3_(k))  …  a_(x_(k) − 1), a_(x_(k))}  with  k = 2 ${US}_{2} = {\left\{ {a_{1_{2}},a_{2_{2}},{a_{3_{2}}\quad \ldots \quad a_{x_{2} - 1}},a_{x_{2}}} \right\} \quad \underset{\_}{{{length}\quad {of}\quad {US}_{2}} = x_{2}}}$

In a further, third method step VS3, a unit length “m” is calculated for both source signals US₁, US₂. This calculation ensues according to the equation:

m=n′*m′  (F1),

whereby n′εN₀ and m′=2^(ent((ld(max{x) ^(_(k−n+1)) ^(, x) ^(_(k)) ^(}))+0,5)

A new length “m” is obtained with this equation such that, proceeding from the longest source signal, the next-higher 2^(n) value is determined. This is the precondition for a Fast Fourier Transformation (FFT) that is applied in a later method step of the flowchart. Over and above this, the function f(z)=ent(z) supplies the highest whole number that is smaller than or equal to z.

Taking k=2, n′=2 and n ε{2 . . . k} into consideration, this yields the equation:

m=2^(1+ent((ld(max{x) ^(₁) ^(, x) ^(₂) ^(}))+0,5)  (F2)

The reason for the selection of n′=2 is that the unit length “m” given an n′2 is so great that an echo (a copy formed from the respective source signal US₁, US₂) formed from the respective source signal US₁, US₂ is not convoluted into the signal region of the respective source signal US₁, US₂. As a result thereof, the source signal is advantageously not influenced in terms of its dynamic properties. When, by contrast, n′=1, then a convolution of the echo or a the copy over the respective source signal occurs.

In a further, fourth method step VS4, the source signals US₁, US₂ are filled with “0” up to the unit length “m”. To that end, a number of “m−x₁” zeros are appended immediately following the last sample or coefficient

given the first source signal US₁, whereas a plurality of “m−x₂” zeros is appended directly following the last sample or coefficient given the second source signal US₂. ${US}_{1}^{\prime} = \left\{ {a_{1_{1}},a_{2_{1}},{a_{3_{1}}\quad \ldots \quad a_{x_{1} - 1}},a_{x_{1}},{{\underset{\backslash {plurality}}{\left. \underset{\_}{0,0,0,{0\quad \ldots \quad 0}} \right\}}\begin{matrix} \quad \\ {{\,_{''}m} - {x_{1}}^{``}} \end{matrix}{US}_{2}^{\prime}} = \left\{ {a_{1_{2}},a_{2_{2}},{a_{3_{2}}\quad \ldots \quad a_{x_{2} - 1}},a_{x_{2}},{\underset{\backslash {plurality}}{\left. \underset{\_}{0,0,0,{0\quad \ldots \quad 0}} \right\}}\begin{matrix} \quad \\ {{\,_{''}m} - {x_{2}}^{``}} \end{matrix}}} \right.}} \right.$

FIG. 5 shows the source signal US₁′ lengthened in this way, whereas FIG. 8 shows the source signal US₂′ lengthened in this way.

In a further, fifth method step VS5, the lengthened source signals US₁, US₂ are transformed into the frequency domain in a known way with the aforementioned Fast Fourier Transformation (FFT), and transformed source signals US₁″, US₂″ are obtained.

US ₁ ″={A ₍₁ ₁₎ e ^(jφ) ^(₁) , A ₍₂ ₁₎ e ^(jφ) ^(₂) , A ₍₃ ₁₎ e ^(jφ) ^(₃) , . . . A _((u) ₁₎ e ^(jφ) ^(_(u)) , A _(((u+1)) ₁₎ e ^(jφ) ^(_(u+1)) },

whereby $u = {\frac{m}{2} - 1}$

US ₂ ″={A ₍₁ ₂₎ e ^(jφ) ^(₁) , A ₍₂ ₂₎ e ^(jφ) ^(₂) , A ₍₃ ₂₎ e ^(jφ) ^(₃) , . . . A _((u) ₂₎ e ^(jφ) ^(_(u)) , A _(((u+1)) ₂₎ e ^(jφ) ^(_(u+1)) },

whereby $u = {\frac{m}{2} - 1}$

FIG. 7 shows the transformed source signal US₁″, whereas FIG. 6 shows the transformed source signal US₂″.

In a sixth method step VS6, individual (specific, predetermined) spectral lines of the transformed source signals US₁″, US₂″ in the frequency domain are multiplied by “0” according to a predetermined criterion, whereas other spectral lines, which obey the same criterion, are multiplied by “1”. The determination as to which spectral lines of the transformed source signals US₁″, US₂″ are multiplied by “0” and which are multiplied by “1” can, for example, ensues on the basis of the following alternance rules:

First rule: US_(1″) 1₁ 0₂ 1₃ 0₄ 1₅ . . . 0 m US_(2″) 0₁ 1₂ 0₃ 1₄ 0₅ . . . 1 m Sum 1 1 1 1 1 1 1 1 1 Second rule: US_(1″) 0₁ 1₂ 0₃ 1₄ 0₅ . . . 1 m US_(2″) 1₁ 0₂ 1₃ 0₄ 1₅ . . . 0 m Sum 1 1 1 1 1 1 1 1 1 Third rule: US_(1″) (b0*1)_(1 . . . b0) (b1*0)_(b0+1 . . .) (b2*1) . . . (b3*0) . . . (b4*1) . . . . . (bx*0) . . . m US_(2″) (b0*0)_(1 . . . b0) (b1*1)_(b0+1 . . .) (b2*0) . . . (b3*1) . . . (b4*0) . . . . . (bx*1) . . . m Sum (b0*1)_(1 . . . b0) (b1*1)_(b0+1 . . .) (b2*1) . . . (b3*1) . . . (b4*1) . . . . . (bx*1) . . . m Fourth rule: US_(1″) (b0*0)_(1 . . . b0) (b1*1)_(b0+1 . . .) (b2*0) . . . (b3*1) . . . (b4*0) . . . . . (bx*1) . . . m US_(2″) (b0*1)_(1 . . . b0) (b1*0)_(b0+1 . . .) (b2*1) . . . (b3*0) . . . (b4*1) . . . . . (bx*0) . . . m Summe (b0*1)_(1 . . . b0) (b1*1)_(b0+1 . . .) (b2*1) . . . (b3*1) . . . (b4*1) . . . . . (bx*1) . . . m

The factors b0 . . . bx indicate how many spectral lines are respectively multiplied by “0” or by “1”. The factors can thereby all be the same or respectively different. Alternating blocks of identical or different block length thus arise. The block lengths and, thus, the factors are advantageously selected such that they match the frequency resolution of human hearing (Bark scale) or are based on the spectral resolution of sub-band algorithms.

The prescribed criterion is that the respective sum of the “zero” multipliers and “one” multipliers by which the spectral lines of the same frequency or same frequency group are multiplied is equal to “1”.

In this way, an orthogonal signal pair SS₁′, SS₂′ that is presented in the frequency domain is acquired from the transformed source signals US₁″, US₂″. Given application of rule 1, the following Fourier values derive for the signal pair SS₁′, SS₂′:

SS ₁ ′={A ₍₁ ₁₎ e ^(jφ) ^(₁) , 0, A ₍₃ ₁₎ e ^(jφ) ^(₃) , . . . A _((u) ₁₎ e ^(jφ) ^(_(u)) , 0},

SS ₂′={0, A ₍₂ ₂₎ e ^(jφ) ^(₂) , 0, . . . 0, A _(((u+1)) ₂₎ e ^(jφ) ^(_(u+1)) },

FIG. 9 shows the spectra of the orthogonal signal pair SS₁′, SS₂′ for a small frequency segment.

In a final, seventh method step VS7, the orthogonal signal pair SS₁′, SS₂′, presented in the frequency domain is transformed into the time domain. As a result of this transformation, one finally obtains orthogonal measured signals SS₁″, SS₂″ that, like the measured signal SS₁, SS₂ of FIG. 1, can be employed for measuring the transmission properties of the handsfree device FSE. The orthogonal measured signal SS₁″ is shown in FIG. 10, whereas the orthogonal measured signal SS₂″ is shown in FIG. 11. It can be seen in FIG. 10 that the orthogonal measured signal SS₁′ is the source signal US₁ with an echo convoluted outside the source signal US₁. The same is true of the orthogonal measured signal SS₂″, which is formed from the source signal US₂ with an echo convoluted outside the source signal US₂.

Generating the orthogonal measured signals SS₁″, SS₂″ from the source signals US₁, US₂ can also ensue directly in the time domain, i.e. without a transformation from the time domain into the frequency domain and a back-transformation from the frequency domain into the time domain. Method steps VS5 and VS7 are thus omitted.

The orthogonal measured signals SS₁″, SS₂″ are obtained in the following way:

1. Generating a copy of the first source signal US₁ and of the second source signal US₂.

2. Attaching the copy behind the respective source signal US₁, US₂.

3. Inverting the signal parts of the copy of the first source signal US₁ and non-modification of the signal parts of the copy of the second source signal US₂. Arising according to FIG. 10 is a signal composed of the first source signal US₁ and an “echo” with inverted operational sign, and, according to FIG. 11, a signal composed of the second source signal US₂ and an “echo” with the proper operational sign.

When the measuring signals SS₁″, SS₂″ are employed when measuring the transmission properties of the handsfree device FSE in the measuring system MS according to FIG. 1, then corresponding reception signals ES₁″, ES₂″ are obtained. These reception signals ES₁″, ES₂″ are processed in the measuring system MS in exactly the same way as the source signals US₁, US₂ (flowchart according to FIG. 2). In this way, signal parts produced by crosstalk can be eliminated.

Although the present invention has been described with reference to specific embodiments, those of skill in the art will recognize that changes may be made thereto without departing from the spirit and scope of the present invention as set forth in the hereafter appended claims. 

What is claimed is:
 1. A method for generating measuring signals for measuring transmission properties of transmission links mutually influencing one another with crosstalk in a telecommunications system, comprising the steps of: generating a plurality k of source signals s; defining a (k−n+1)^(th) source signal length x_(k−n+1) of a (k−n+1)^(th) source signal s_(k−n+1) with x_(k−n+1) SIGNAL parts a ₁ _(k−n+1) , a ₂ _(k−n+1) , a ₃ _(k−n+1) . . . a _(x) _(k−n+1) ⁻¹ , a _(x) _(k−n+1) , said source signal length x being x 0, and said coefficient n being n{2 . . . k}; defining a k^(th) source signal length x^(k) of a k^(th) source signal s_(k) with x^(k) signal parts a ₁ _(k) , a ₂ _(k) , a ₃ _(k) . . . a _(x) _(k) ⁻¹ , a _(x) _(k) ; calculating a measuring signal length m as m=n′m′, said n being n′ 0 and said m′ being m′=2^(ent((ld(max{x) ^(_(k−n+1)) ^(, x) ^(_(k)) ^(}))+0,5); lengthening said (k−n+1)^(th) source signal s_(k−n+1) to said measuring signal length m by attaching m−x_(k−n+1) zeros to an end of said (k−n+1)^(th) source signal s_(k−n+1); lengthening said k^(th) source signal s_(k) to said measuring signal length m by attaching m−x_(k) zeros to an end of said k^(th) source signal s_(k); and modifying said lengthened (k−n+1)^(th) source signal s_(k−n+1), and said lengthened k^(th) source signal s_(k) such that said (k−n+1)^(th) source signal s_(k−n+1) and said k^(th) source signal s_(k) being essentially orthogonal.
 2. The method according to claim 1, wherein said (k−n+1)^(th) source signal s_(k−n+1), and said k^(th) source signal s_(k) having an orthogonality relationship |(s_(k−n+1), s_(k))|<<|s_(k−n+1| and |(s) _(k−n+1), s_(k))|<<|s_(k)|.
 3. The method according to claim 1, further comprising the steps of: generating spectral lines of said lengthened (k−n+1)^(th) source signals s_(k−n+1) and said k^(th) source signals s_(k) by transforming said (k−n+1)^(th) source signals s_(k−n+1) into a frequency domain; multiplying said spectral lines by zero and one in alternation and alternatively in alternation by blocks such that a sum of said zero multipliers and one multipliers by which said spectral lines of a same frequency and alternatively same frequency group are multiplied is equal to 1; and transforming said (k−n+1)^(th) source signals s_(k−n+1) and said k^(th) source signals s_(k) modified with respect to said spectral lines into a time domain.
 4. The method according to claim 3, wherein said alternating blocks of said spectral lines at least have a uniform length.
 5. The method according to claim 1, wherein said step of generating a plurality k of source signals further comprises generating two (k=2) source signals, a first source signal S₁ and a second source signal S₂; and further comprising the steps of: generating a first copy of said first source signal S₁ and a second copy of said second source signal S₂; attaching said generated first copy behind said first source signal S₁ and said generated second copy behind said second source signal S₂; and inverting said signal parts of one of said first and second copies.
 6. The method according to claim 5, wherein said calculated measuring signal length m being equal to 2m′ (n′=2).
 7. A device for measuring transmission properties of transmission links mutually influencing one another with crosstalk in a telecommunications system, comprising: a measuring system for generating measuring signals, said measuring signals being generated by: generating a plurality k of source signals s; defining a (k−n+1)^(th) source signal length x_(k−n+1) of a (k−n+1)^(th) source signal s_(k−n+1) with x_(k−n+1) signal parts a ₁ _(k−n+1) , a ₂ _(k−n+1) , a ₃ _(k−n+1) . . . a _(x) _(k−n+1) ⁻¹ , a _(x) _(k−n+1) , said source signal length x being x< >0, and said coefficient n being n{2 . . . k}; defining a k^(th) source signal length x_(k) of a k^(th) source signal s_(k) with x_(k) signal parts a ₁ _(k) , a ₂ _(k) , a ₃ _(k) . . . a _(x) _(k) ⁻¹ , a _(x) _(k) ; calculating a measuring signal length m as m=n′m′, said n being n′ 0 and said m′ being m′=2^(ent((ld(max{x) ^(_(k−n+1)) ^(, x) _(}))+0.5) ^(_(k)) lengthening said (k−n+1)^(th) source signal s_(k−n+1) to said measuring signal length m by attaching m−x_(k−n+1) zeros to an end of said (k−n+1)^(th) source signal s_(k−n+1); lengthening said k^(th) source signal s_(k) to said measuring signal length m by attaching m−x_(k) zeros to an end of said k^(th) source signal s_(k); and modifying said lengthened (k−n+1)^(th) source signal s_(k−n+1) and said lengthened k^(th) source signal s_(k) such that said (k−n+1)^(th) source signal s_(k−n+1) and said k^(th) source signal s_(k) being essentially orthogonal. 